Download: • Single Supply, 5.0 V to 12 V TECHNICAL DATA • Channel 3 or 4 Operation • Variable Gain RF Modulator • Wide Dynamic Range • Low Intermodulation Distortion

Order this document by MC1374/D The MC1374 includes an FM audio modulator, sound carrier oscillator, RF oscillator, and RF dual input modulator. It is designed to generate a TV signal from audio and video inputs. The MC1374’s wide dynamic range and low TV MODULATOR CIRCUIT distortion audio make it particularly well suited for applications such as video tape recorders, video disc players, TV games and subscription decoders. SEMICONDUCTOR • Single Supply, 5.0 V to 12 V TECHNICAL DATA • Channel 3 or 4 Operation • Variable Gain RF Modulator • Wide Dynamic Range • Low Intermodulation Distortion • P...
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Order this document by MC1374/D The MC1374 includes an FM audio modulator, sound carrier oscillator, RF oscillator, and RF dual input modulator. It is designed to generate a TV signal from audio and video inputs. The MC1374’s wide dynamic range and low TV MODULATOR CIRCUIT distortion audio make it particularly well suited for applications such as video tape recorders, video disc players, TV games and subscription decoders. SEMICONDUCTOR • Single Supply, 5.0 V to 12 V TECHNICAL DATA • Channel 3 or 4 Operation • Variable Gain RF Modulator • Wide Dynamic Range • Low Intermodulation Distortion • Positive or Negative Sync 14 • Low Audio Distortion 1 • Few External Components P SUFFIX PLASTIC PACKAGE CASE 646 ORDERING INFORMATION Operating Device Temperature Range Package MC1374P TA = 0° to +70°C Plastic DIP Figure 1. Simplified Application

V

Channel34+V = 12V4V+ CC Pin 1 VPin 11 + S1 C8 C9 0.001 R10 0.001 R1 10k 3 5–25 D1 t C1 R3 C7 MPN3404 0.001 47078R7 75Ω 0.22µH 0.22µH C15 L1 C2 L3 L4 0.0015669Output R2 5 10 C11 C12 C13470 22 47 22 R9 + 4 U1 11 560+ C14 MC1374 D2C16 R14 R11 0.01 3 12 1N91456k C4 C3 47 + 220 R4 50 120 + L2 R8 C102 13 6.8k 2.2k R12 10µF Video In C5 180k 0.001 1 14 + Audio In R6 R5 2.2k R13 C6 3.3k Shaded Parts Optional 30k 1µF L1 – 4 Turns #22, 1/4″ Dia. L2 – 40 Turns, #36, 3/16″ Dia. Motorola, Inc. 1996 Rev 0 MOTOROLA ANALOG IC DEVICE DATA 1, MAXIMUM RATINGS (TA = 25°C, unless otherwise noted.) Rating Value Unit Supply Voltage 14 Vdc Operating Ambient Temperature Range 0 to +70 °C Storage Temperature Range –65 to +150 °C Junction Temperature 150 °C Power Dissipation Package 1.25 W Derate above 25°C 10 mW/°C ELECTRICAL CHARACTERISTICS (VCC = 12 Vdc, TA = 25°C, fc = 67.25 MHz, Figure 4 circuit, unless otherwise noted.) Characteristics Min Typ Max Unit AM OSCILLATOR/MODULATOR Operating Supply Voltage 5.0 12 12 V Supply Current (Figure 1) – 13 – mA Video Input Dynamic Range (Sync Amplitude) 0.25 1.0 1.0 V Pk RF Output (Pin 9, R7 = 75 Ω, No External Load) – 170 – mV pp Carrier Suppression 36 40 – dB Linearity (75% to 12.5% Carrier, 15 kHz to 3.58 MHz) – – 2.0 % Differential Gain Distortion (IRE Test Signal) 5.0 7.0 10 % Differential Phase Distortion (3.58 MHz IRE Test Signal) – 1.5 2.0 Degrees 920 kHz Beat (3.58 MHz @ 30%, 4.5 MHz @ 25%) – –57 – dB Video Bandwidth (75 Ω Input Source) 30 – – MHz Oscillator Frequency Range – 105 – MHz Internal Resistance across Tank (Pin 6 to Pin 7) – 1.8 – kΩ Internal Capacitance across Tank (Pin 6 to Pin 7) – 4.0 – pF ELECTRICAL CHARACTERISTICS (TA = 25°C, VCC = 12 Vdc, 4.5 MHz, Test circuit of Figure 11, unless otherwise noted.) Characteristics Min Typ Max Unit FM OSCILLATOR/MODULATOR Frequency Range of Modulator 14 4.5 14 MHz Frequency Shift versus Temperature (Pin 14 open) – 0.2 0.3 kHz/°C Frequency Shift versus VCC (Pin 14 open) – – 4.0 kHz/V Output Amplitude (Pin 3 not loaded) – 900 – mVpp Output Harmonics, Unmodulated – – –40 dB Modulation Sensitivity 1.7 MHz – 0.20 – MHz/V 4.5 MHz – 0.24 – 10.7 MHz – 0.80 – Audio Distortion (±25 kHz Deviation, Optimized Bias Pin 14) – 0.6 1.0 % Audio Distortion (±25 kHz Deviation, Pin 14 self biased) – 1.4 – Incidental AM (±25 kHz FM) – 2.0 – Audio Input Resistance (Pin 14 to ground) – 6.0 – kΩ Audio Input Capacitance (Pin 14 to ground) – 5.0 – pF Stray Tuning Capacitance (Pin 3 to ground) – 5.0 – pF Effective Oscillator Source Impedance (Pin 3 to load) – 2.0 – kΩ 2 MOTOROLA ANALOG IC DEVICE DATA, Figure 2. TV Modulator Bias FM Oscillator/Modulator AM Modulator AM Oscillator Section Sound Carrier Sound Carrier Audio In OSC B+ Oscillator VCC RF Out RF Tank 144328976R10 R11 R12 R16 6.0k Q7 Q21 Q22 Q1 Q2 R13 325 Q19 Q20 Q12 Q13 Q14 Q15 R17 Q25 C1 Q24 R14 Q3 Q6 Q4 Q5 Q10 Q11 R15 Q26 Q27 Q8 Q9 Q16 Q17 Q23 Q18 D1 R1 R2 R3 R4 R5 R6 R7 R8 R95113 12 11 Gnd Sound Carrier Gain Video In In

GENERAL INFORMATION

The MC1374 contains an RF oscillator, RF modulator, and base station (1.76 MHz), and high enough to be used as an a phase shift type FM modulator, arranged to permit good FM IF test signal source (10.7 MHz). At 4.5 MHz, a deviation printed circuit layout of a complete TV modulation system. of ±25 kHz can be achieved with 0.6% distortion (typical). The RF oscillator is similar to the one used in MC1373, and is In the circuit above, devices Q1 through Q7 are active in coupled internally in the same way. Its frequency is controlled the oscillator function. Differential amplifier Q3, Q4, Q5, and by an external tank on Pins 6 and 7, or by a crystal circuit, and Q6 acts as a gain stage, sinking current from input section will operate to approximately 105 MHz. The video modulator Q1, Q2 and the phase shift network R17, C1. Input amplifier is a balanced type as used in the well known MC1496. Q1, Q2 can vary the amount of “in phase” Q4 current to be Modulated sound carrier and composite video information combined with phase shifter current in load resistor R16. The can be put in separately on Pins 1 and 11 to minimize R16 voltage is applied to emitter follower Q7 which drives an unwanted crosstalk. A single resistor on Pins 12 and 13 is external L–C circuit. Feedback from the center of the L–C selected to set the modulator gain. The RF output at Pin 9 is circuit back to the base of Q6 closes the loop. As audio input a current source which drives a load connected from Pin 9 to is applied which would offset the stable oscillatory phase, the VCC. frequency changes to counteract. The input to Pin 14 can The FM system was designed specifically for the TV include a dc feedback current for AFC over a limited range. intercarrier function. For circuit economy, one phase shift The modulated FM signal from Pin 3 is coupled to Pin 1 of circuit was built into the ship. Still, it will operate from 1.4 MHz the RF modulator and is then modulated onto the AM carrier. to 14 MHz, low enough to be used in a cordless telephone MOTOROLA ANALOG IC DEVICE DATA3I1= 1.15 mAI1= 1.15 mAI2= 1.15 mA, AM Section The AM modulator transfer function in Figure 3 shows that In television, one of the most serious concerns is the the video input can be of either polarity (and can be applied at prevention of the intermodulation of color (3.58 MHz) and either input). When the voltages on Pin 1 and Pin 11 are sound (4.5 MHz) frequencies, which causes a 920 kHz signal equal, the RF output is theoretically zero. As the difference to appear in the spectrum. Very little (3rd order) nonlinearity is between VPin 11 and VPin 1 increases, the RF output needed to cause this problem. The results in Figure 6 are increases linearly until all of the current from both I1 current unsatisfactory, and demonstrate that too much of the sources (Q8 and Q9) is flowing in one side of the modulator. available dynamic range of the MC1374 has been used. This occurs when ±(VPin11 – VPin1) = I1 RG, where I1 is Figures 8 and 10 show that by either reducing standard typically 1.15 mA. The peak–to–peak RF output is the 2I1 RL. signal level, or reducing gain, acceptable results may be Usually the value of RL is chosen to be 75 Ω to ease the obtained. design of the output filter and match into TV distribution At VHF frequencies, small imbalances within the device systems. The theoretical range of input voltage and RG is introduce substantial amounts of 2nd harmonic in the RF quite wide, but noise and available sound level limit the useful output. At 67 MHz, the 2nd harmonic is only 6 to 8 dB below video (sync tip) amplitude to between 0.25 Vpk and 1.0 Vpk. the maximum fundamental. For this reason, a double pi low It is recommended that the value of RG be chosen so that pass filter is shown in the test circuit of Figure 3 and works only about half of the dynamic range will be used at sync tip well for Channel 3 and 4 lab work. For a fully commercial level. application, a vestigial sideband filter will be required. The The operating window of Figure 5 shows a cross–hatched general form and approximate values are shown in Figure 19. area where Pin 1 and Pin 11 voltages must always be in order It must be exactly aligned to the particular channel. to avoid saturation in any part of the modulator. The letter φ represents one diode drop, or about 0.75 V. The oscillator Pins 6 and 7 must be biased to a level of VCC – φ – 2I1 RL (or Figure 3. AM Modulator Transfer Function lower) and the input Pins 1 and 11 must always be at least 2φ below that. It is permissible to operate down to 1.6 V, saturating the current sources, but whenever possible, the minimum should be 3φ above ground. 2I R The oscillator will operate dependably up to about1L105 MHz with a broad range of tank circuit component values. It is desirable to use a small L and a large C to minimize the dependence on IC internal capacitance. An operating Q between 10 and 20 is recommended. The values of R1, R2 and R3 are chosen to produce the desired Q and to set the Pin 6 and 7 dc voltage as discussed above. –I1RG 0 +I1RG Unbalanced operation, i.e., Pin 6 or 7 bypassed to ground, is Differential Input, V –V (V) not recommended. Although the oscillator will still run, and 11 1 the modulator will produce a useable signal, this mode causes substantial base–band video feedthrough. Bandswitching, as Figure 1 shows, can still be accomplished Figure 4. AM Test Circuit economically without using the unbalanced method. R2 The oscillator frequency with respect to temperature in the 470 test circuit shows less than ±20 kHz total shift from 0° to 50°C as shown in Figure 7. At higher temperatures the slope L1 0.1µH approaches 2.0 kHz/°C. Improvement in this region would 470 0.001 require a temperature compensating tuning capacitor of the C2 56 R3 N75 family. R1 Crystal control is feasible using the circuit shown in Figure 470 21. The crystal is a 3rd overtone series type, used in series67resonance. The L1, C2 resonance is adjusted well below the crystal frequency and is sufficiently tolerant to permit fixed V118VCC values. A frequency shift versus temperature of less than 1.0 Hz/°C can be expected from this approach. The resistors RL Ra and Rb are to suppress parasitic resonances. 10µF RF + Coupling of output RF to wiring and components on Pins 1 11 9 and 11 can cause as much as 300 kHz shift in carrier (at Video 22µH 22µH 67 MHz) over the video input range. A careful layout can Input 22 47 22 keep this shift below 10 kHz. Oscillator may also be 1.0k 12 13 5 inadvertently coupled to the RF output, with the undesired effect of preventing a good null when V11 = V1. Reasonable care will yield carrier rejection ratios of 36 to 40 dB below sync V11 RG tip level carrier. 4 MOTOROLA ANALOG IC DEVICE DATA RF Output V(p–p),

Figure 5. The Operating Window Figure 6. 920 kHz Beat

12 0

R

11 L = 75ΩI= 1.15 mA Initial Video = 1.0 Vdc1 VCC –1010 Chroma (3.58 MHz) = 300 mVppVCC – 2I1RL Sound (4.5 MHz) a) = 250 mVpp 9.0 VCC – φ – 2I1R –20L b) = 500 mVpp 8.0 V – 3φ – 2I R –30 Gain Resistor RG = 1.0 kΩ 7.0 CC 1 L3φ 6.0 Recommended –40 5.0 V1 & V b 4.0 Operating Region –50 a 3.0 –60 2.0 Absolute Min = 1.6 V 1.0 (2φ + Sat) –70 0 –80 5.0 6.0 7.0 8.0 9.0 10 11 12 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 VCC, SUPPLY VOLTAGE (Vdc) DIFFERENTIAL INPUT (V11 – V1) [Vdc)

Figure 7. RF Oscillator Frequency

versus Temperature Figure 8. 920 kHz Beat 1000fc ≈ 61.25 MHz –10 Initial Video = 0.5 Vdc VCC = 12 Vdc Chroma (3.58 MHz) = 150 mVpp –10 –20 Sound (4.5 MHz) a) = 125 mVpp b) = 250 mVpp –20 –30 Gain Resistor RG = 1.0 kΩ –30 –40 –40 –50 b –50 –60 a –60 –70 –70 –80 0 25 50 75 100 0 0.1 0.2 0.3 0.4 0.5 0.6 0.7 0.8 0.9 1.0 1.1 1.2 1.3 1.4 TA, AMBIENT TEMPERATURE (°C) DIFFERENTIAL INPUT (V11 – V1) [Vdc)

Figure 9. RF Oscillator Frequency

versus Supply Voltage Figure 10. 920 kHz Beat 1000–10 Initial Video = 1.0 Vdc Chroma (3.58 MHz) = 300 mVpp –10 –20 Sound (4.5 MHz) a) = 250 mVpp b) = 500 mVpp –20 –30 Gain Resistor (RG) = 2.2 kΩ –30 –40 –40 –50 b –50 TA = 25°C fc = 61.25 MHz –60 a –60 –70 –70 –80 5.0 6.0 7.0 8.0 9.0 10 11 12 0 0.2 0.4 0.6 0.8 1.0 1.2 1.4 1.5 1.6 1.8 2.0 2.2 2.4 2.8 VCC, SUPPLY VOLTAGE (V) DIFFERENTIAL INPUT (V11 – V1) [Vdc)

MOTOROLA ANALOG IC DEVICE DATA 5

NORMALIZED FREQUENCY (kHz) FREQUENCY SHIFT (kHz) AM MODULATOR INPUT VOLTAGE PIN 1 OR PIN 11 (V) (fc ± 920 kHz) AMPLITUDE (fc ± 920 kHz) AMPLITUDE (fc ± 920 kHz) AMPLITUDE [dB] [dB] [dB] (fc) AMPLITUDE (fc) AMPLITUDE (fc) AMPLITUDE, FM Section The oscillator center is approximately the resonance of the The source impedance of Pin 3 is approximately 2.0 kΩ, and inductor L2 from Pin 2 to Pin 3 and the effective capacitance the open circuit amplitude is about 900 mV pp for the test C3 from Pin 3 to ground. For overall oscillator stability, it is circuit shown in Figure 11. best to keep XL in the range of 300 Ω to 1.0 kΩ. The appl icat ion circuit of Figure 1 shows the The modulator transfer characteristic at 4.5 MHz is shown recommended approach to coupling the FM output from Pin 3 in Figure 15. Transfer curves at other frequencies have a very to the AM modulator input, Pin 1. The input impedance at Pin similar shape, but differ in deviation per input volt, as shown in 1 is very high, so the intercarrier level is determined by the Figures 13 and 17. source impedance of Pin 3 driving through C4 into the video Most applications will not require DC connection to the bias circuit impedance of R4 and R5, about 2.2 k. This audio input, Pin 14. However, some improvements can be provides an intercarrier level of 500 mV pp, which is correct achieved by the addition of biasing circuitry. The unaided for the 1.0 V peak video level chosen in this design. Resistor device will establish its own Pin 14 bias at 4 θ, or about 3.0 V. R6 and the input capacitance of Pin 1 provide some This bias is a little too high for optimum modulation linearity. decoupling of stray pickup of RF oscillator or AM output which Figure 14 shows better than 2 to 1 improvement in distortion may be coupled to the sound circuitry. between the unaided device and pulling Pin 14 down to 2.6 V to 2.7 V. This can be accomplished by a simple divider, if the supply voltage is relatively constant. Figure 11. FM Test Circuit The impedance of the divider has a bearing on the f C3 L2 frequency versus temperature stability of the FM system. A o(MHz) (pF) (µH) V divider of 180 kΩ and 30 kΩ (for V CCCC = 12 V) will give good temperature stabilization results. However, as Figure 18 10.7 12 10 shows, a divider is not a good method if the supply voltage 4.5 120 10 varies. The designer must make the decisions here, based 1.76 200 40 on considerations of economy, distortion and temperature78requirements and power supply capability. If the distortion C14 requirements are not stringent, then no bias components are 0.01µF69needed. If, in this case, the temperature compensation needs to be improved in the high ambient area, the tuning capacitor 5 10 from Pin 3 to ground can be selected from N75 or N150 4 11 temperature compensation types. Intercarrier L2 Another reason for DC input to Pin 14 is the possibility of Sound Output 10µH 3 12 automatic frequency control. Where high accuracy of (Use FET Probe) C5 inter–carrier frequency is required, it may be desirable to feed C3 2 13 R12 C6 back the DC output of an AFC or phase detector for nominal 120pF 0.001 + 1µF carrier frequency control. Only limited control range could be µF 1 14 Audio used without adversely affecting the distortion performance, R13 Input but very little frequency compensation will be needed. Optional Bias R One added convenience in the FM section is the separate (See Text) Pin “oscillator B+” which permits disabling of the sound system during alignment of the AM section. Usually it can be hard wired to the VCC source without decoupling. Figure 12. Modulator Sensitivity Standard practice in television is to provide pre–emphasis 2.0 of higher audio frequencies at the transmitter and a matching de–emphasis in the TV receiver audio amplifier. The purpose 1.8 of this is to counteract the fact that less energy is usually 1.6 TA = 25°C present in the higher frequencies, and also that fewer 1.4 modulation sidebands are within the deviation window. Both 1.2 factors degrade signal to noise ration. Pre–emphasis of 75 µs 1.0 is standard practice. For cases where it has not been provided, a suitable pre–emphasis network is covered in 0.8 Figure 20. 0.6 It would seem natural to take the FM system output from 0.4 Pin 2, the emitter follower output, but this output is high in 0.2 harmonic content. Taking the output from Pin 3 sacrifices 0 somewhat in source impedance but results in a clean output 1.4 2.0 3.0 4.0 5.0 6.0 7.0 8.0 9.0 10 14 fundamental, with all harmonics more than 40 dB down. This fosc, OSCILLATOR FREQUENCY [MHz] choice removes the need for additional filtering components. 6 MOTOROLA ANALOG IC DEVICE DATA MAXIMUM CENTER-FREQUENCY SLOPE ( ∆ f/∆ Vi n ) (MHz/V),

Figure 13. Modulator Transfer Function Figure 14. Distortion versus Modulation Depth

2.1 5.0 TA = 25°C 2.0 (1.76 MHz) V = 12 V VCC = 12 VCC T = 25°C 4.0 A 1.9 fc = 4.5 MHzVCC = 5.0 V, 9.0 V 1.8 3.0 Self Bias (2.9–3.0 V) 1.7 1.6 2.0 Optimum Bias (2.6–2.7 V) 1.5 1.0 1.4 1.3001.0 2.0 3.0 4.0 5.0 6.0 7.0 0 25 50 75 100 DC INPUT VOLTAGE, PIN 14 (V) DEVIATION (kHz)

Figure 16. FM System Frequency Figure 15. Modulator Transfer Function versus Temperature

4.9 4.55 TA = 25°C 4.8 (4.5 MHz) VCC = 12 V 4.54 VCC = 12 V 4.7 VCC = 5.0 V, 9.0 V 4.53 Pin 14 V to 2.6 V 4.6 4.52 4.5 4.51 180 k/30 k Divider 4.4 4.50 4.3 4.49 Pin 14 Open 4.2 4.48 4.1 4.47 0 1.0 2.0 3.0 4.0 5.0 6.0 7.0 0 25 50 75 100 DC INPUT VOLTAGE, PIN 14 (V) TA, AMBIENT TEMPERATURE (°C)

Figure 17. Modulator Transfer Function Figure 18. FM System Frequency versus VCC

11.6 T = 25°C 12 V 4.50 A Pin 14 to 2.6 V Source9.0VV11.4 CC(10.7 MHz) 5.0 V 4.49 11.2 4.48 11.0 Pin 14 Open 4.47 10.8 10.6 4.46 Pin14 – 180 k/ 30 k Divider 10.4 4.45 10.2 4.44 10.0 TA = 25°C 9.8 4.43 9.6 4.42 0 1.0 2.0 3.0 4.0 5.0 6.0 7.0 4.0 5.0 6.0 7.0 8.0 9.0 10 11 12 DC INPUT VOLTAGE, PIN 14 (V) VCC, SUPPLY VOLTAGE (Vdc)

MOTOROLA ANALOG IC DEVICE DATA 7

fosc, OSCILLATOR FREQUENCY (MHz) fosc, OSCILLATOR FREQUENCY (MHz) fosc, OSCILLATOR FREQUENCY (MHz) f, FREQUENCY (MHz) f, FREQUENCY (MHz) DISTORTION (%),

Figure 19. A Channel 4 Vestigial Sideband Filter VCC

Both transformer windings 0 RL = 75Ω 8.2pF 4T #23 AWG –109 close wound on 1/4″ ID –20 24Ω 39 on common axis, 3/8″ spacing.2.7k –30pF –40 33pF Ch. 4 Ch. 4 8.2pF –5024Ω 24Ω Output Pix S–60 75Ω –70 33pF 33pF 100Ω 61 65 69 73 f, FREQUENCY (MHz) 8T #23 AWG close wound on 1/8″ ID, knife tuned to trap Channel 3 61.25 MHz.

Figure 20. Audio Pre–Emphasis Circuit

252πRC C = 0.0012µF 15 CC = 0.1µF – + 14 1011“Flat” AudioR52π(r + R)C2πrCC Audio Input 6.0kΩr = 56kΩ Input05Gnd –5 21 210 2100 21k f, FREQUENCY (MHz) Pre–emphasis = 75 µs = rC = 2 π (2100 Hz)

Figure 21. Crystal Controlled RF Oscillator

for Channel 3, 61.25 MHz

VCC

R1 470 C1 0.001 R2 470 R3 470 61.252 MHz C2 56pF Ra L1 0.15µH Rb 1867MC1374

NOTE: See Application Note AN829 for further information.

8 MOTOROLA ANALOG IC DEVICE DATA RELATIVE OUTPUT/INPUT (dB) ATTENUATION (dB),

OUTLINE DIMENSIONS P SUFFIX PLASTIC PACKAGE CASE 646–06 NOTES: ISSUE L 1. LEADS WITHIN 0.13 (0.005) RADIUS OF TRUE

14 8 POSITION AT SEATING PLANE AT MAXIMUM MATERIAL CONDITION.

B 2. DIMENSION L TO CENTER OF LEADS WHEN

FORMED PARALLEL. 1 7 3. DIMENSION B DOES NOT INCLUDE MOLD FLASH. 4. ROUNDED CORNERS OPTIONAL.

A INCHES MILLIMETERS

DIM MIN MAX MIN MAX

FLA0.715 0.770 18.16 19.56

B 0.240 0.260 6.10 6.60 C 0.145 0.185 3.69 4.69 D 0.015 0.021 0.38 0.53

C F 0.040 0.070 1.02 1.78

G 0.100 BSC 2.54 BSC

J H 0.052 0.095 1.32 2.41N J 0.008 0.015 0.20 0.38

SEATING K 0.115 0.135 2.92 3.43 PLANEKL0.300 BSC 7.62 BSC

HGDMM010 0 10

N 0.015 0.039 0.39 1.01

MOTOROLA ANALOG IC DEVICE DATA 9

, Motorola reserves the right to make changes without further notice to any products herein. Motorola makes no warranty, representation or guarantee regarding the suitability of its products for any particular purpose, nor does Motorola assume any liability arising out of the application or use of any product or circuit, and specifically disclaims any and all liability, including without limitation consequential or incidental damages. “Typical” parameters which may be provided in Motorola data sheets and/or specifications can and do vary in different applications and actual performance may vary over time. All operating parameters, including “Typicals” must be validated for each customer application by customer’s technical experts. Motorola does not convey any license under its patent rights nor the rights of others. Motorola products are not designed, intended, or authorized for use as components in systems intended for surgical implant into the body, or other applications intended to support or sustain life, or for any other application in which the failure of the Motorola product could create a situation where personal injury or death may occur. Should Buyer purchase or use Motorola products for any such unintended or unauthorized application, Buyer shall indemnify and hold Motorola and its officers, employees, subsidiaries, affiliates, and distributors harmless against all claims, costs, damages, and expenses, and reasonable attorney fees arising out of, directly or indirectly, any claim of personal injury or death associated with such unintended or unauthorized use, even if such claim alleges that Motorola was negligent regarding the design or manufacture of the part. Motorola and are registered trademarks of Motorola, Inc. Motorola, Inc. is an Equal Opportunity/Affirmative Action Employer. How to reach us: USA/EUROPE/Locations Not Listed: Motorola Literature Distribution; JAPAN: Nippon Motorola Ltd.; Tatsumi–SPD–JLDC, 6F Seibu–Butsuryu–Center, P.O. Box 20912; Phoenix, Arizona 85036. 1–800–441–2447 or 602–303–5454 3–14–2 Tatsumi Koto–Ku, Tokyo 135, Japan. 03–81–3521–8315 MFAX: email is hidden – TOUCHTONE 602–244–6609 ASIA/PACIFIC: Motorola Semiconductors H.K. Ltd.; 8B Tai Ping Industrial Park, INTERNET: http://Design–NET.com 51 Ting Kok Road, Tai Po, N.T., Hong Kong. 852–26629298 10 ◊ MOTOROLA ANALOG IC DEMVICC1E37 D4/ADTA]
15

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